Semiconductor-element-including memory device

ABSTRACT

A memory device includes pages arranged in columns and each constituted by a plurality of memory cells on a substrate, voltages applied to a first gate conductor layer, a second gate conductor layer, a first impurity layer, and a second impurity layer in each memory cell included in each of the pages are controlled to perform a page write operation of retaining, inside a channel semiconductor layer, a group of positive holes generated by an impact ionization phenomenon or by a gate-induced drain leakage current, and the voltages applied to the first gate conductor layer, the second gate conductor layer, the first impurity layer, and the second impurity layer are controlled to perform a page erase operation of discharging the group of positive holes from inside the channel semiconductor layer. The first impurity layer of the memory cell is connected to a source line, the second impurity layer thereof is connected to a bit line, one of the first gate conductor layer or the second gate conductor layer thereof is connected to a word line, the other of the first gate conductor layer or the second gate conductor layer thereof is connected to a driving control line, and the bit lines are connected to sense amplifier circuits with a switch circuit therebetween. In a page read operation, page data in a group of memory cells selected by the word line is read to the sense amplifier circuits, and in a page sum-of-products read operation, a voltage is applied to the driving control line such that memory cell currents, in the group of memory cells, flowing into the bit lines multiply N-fold (N is a positive integer).

CROSS-REFERENCE TO RELATED APPLICATIONS

This application claims priority under 35 U.S.C. §119(a) to PCT/JP2021/018409 filed May 14, 2021, the enter content of which is incorporated herein by reference.

TECHNICAL FIELD

The present invention relates to a semiconductor-element-including memory device.

BACKGROUND ART

Recently, there has been a demand for highly integrated and high-performance memory elements in the development of LSI (Large Scale Integration) technology.

Typical planar MOS transistors include a channel that extends in a horizontal direction along the upper surface of the semiconductor substrate. In contrast, SGTs include a channel that extends in a direction perpendicular to the upper surface of the semiconductor substrate (see, for example, PTL 1 and NPL 1). Accordingly, the density of semiconductor devices can be made higher with SGTs than with planar MOS transistors. Such SGTs can be used as selection transistors to implement highly integrated memories, such as a DRAM (Dynamic Random Access Memory, see, for example, NPL 2) to which a capacitor is connected, a PCM (Phase Change Memory, see, for example, NPL 3) to which a resistance change element is connected, an RRAM (Resistive Random Access Memory, see, for example, NPL 4), and an MRAM (Magneto-resistive Random Access Memory, see, for example, NPL 5) that changes the resistance by changing the orientation of a magnetic spin with a current. Further, there exists, for example, a DRAM memory cell (see, for example, NPL 6) constituted by a single MOS transistor and including no capacitor. The present application relates to a dynamic flash memory that can be constituted only by a MOS transistor and that includes no resistance change element or capacitor.

FIGS. 7A to 7D illustrate a write operation of a DRAM memory cell constituted by a single MOS transistor and including no capacitor described above, FIGS. 8A and B illustrate a problem in the operation, and FIGS. 9A to C illustrate a read operation (see NPL 7 to NPL 10). FIG. 7A illustrates a “1” write state. Here, the memory cell is formed on an SOI substrate 100, is constituted by a source N⁺ layer 103 (hereinafter, a semiconductor region that contains a donor impurity in high concentrations is referred to as “N⁺ layer”) to which a source line SL is connected, a drain N⁺ layer 104 to which a bit line BL is connected, a gate conductor layer 105 to which a word line WL is connected, and a floating body 102 of a MOS transistor 110, and includes no capacitor. The single MOS transistor 110 constitutes the DRAM memory cell. Directly under the floating body 102, a SiO₂ layer 101 of the SOI substrate is in contact with the floating body 102. To write “1” to the memory cell constituted by the single MOS transistor 110, the MOS transistor 110 is operated in the saturation region. That is, a channel 107, for electrons, extending from the source N⁺ layer 103 has a pinch-off point 108 and does not reach the drain N⁺ layer 104 to which the bit line is connected. When a high voltage is applied to both the bit line BL connected to the drain N⁺ layer and the word line WL connected to the gate conductor layer 105, and the MOS transistor 110 is operated at the gate voltage that is about one-half of the drain voltage, the electric field intensity becomes maximum at the pinch-off point 108 that is in the vicinity of the drain N⁺ layer 104. As a result, accelerated electrons that flow from the source N⁺ layer 103 toward the drain N⁺ layer 104 collide with the Si lattice, and with kinetic energy lost at the time of collision, electron-positive hole pairs are generated (impact ionization phenomenon). Most of the generated electrons (not illustrated) reach the drain N⁺ layer 104. Further, a very small proportion of the electrons that are very hot pass through a gate oxide film 109 and reach the gate conductor layer 105. Simultaneously, positive holes 106 are generated with which the floating body 102 is charged. In this case, the generated positive holes contribute to an increase in the majority carriers because the floating body 102 is P-type Si. When the floating body 102 is filled with the generated positive holes 106 and the voltage of the floating body 102 becomes higher than that of the source N⁺ layer 103 by Vb or more, further generated positive holes are discharged to the source N⁺ layer 103. Here, Vb is the built-in voltage of the PN junction between the source N⁺ layer 103 and the P layer, namely, the floating body 102, and is equal to about 0.7 V. FIG. 7B illustrates a state in which the floating body 102 is charged to saturation with the generated positive holes 106.

Now, a “0” write operation of the memory cell 110 will be described with reference to FIG. 7C. For the common selection word line WL, the memory cell 110 to which “1” is written and the memory cell 110 to which “0” is written are present at random. FIG. 7C illustrates a state of rewriting from the “1” write state to a “0” write state. To write “0”, the voltage of the bit line BL is set to a negative bias, and the PN junction between the drain N⁺ layer 104 and the P layer, namely, the floating body 102, is forward biased. As a result, the positive holes 106 in the floating body 102 generated in advance in the previous cycle flow into the drain N⁺ layer 104 that is connected to the bit line BL. When the write operation ends, the two memory cells are in a state in which the memory cell 110 (FIG. 7B) is filled with the generated positive holes 106, and from the memory cell 110 (FIG. 7C), the generated positive holes are discharged. The potential of the floating body 102 of the memory cell 110 filled with the positive holes 106 becomes higher than that of the floating body 102 in which generated positive holes are not present. Therefore, the threshold voltage for the memory cell 110 to which “1” is written becomes lower than the threshold voltage for the memory cell 110 to which “0” is written. This is illustrated in FIG. 7D.

Now, a problem in the operation of the memory cell constituted by the single MOS transistor 110 will be described with reference to FIGS. 8A and 8B. As illustrated in FIG. 8A, the capacitance C_(FB) of the floating body is equal to the sum of the capacitance C_(WL) between the gate to which the word line is connected and the floating body, the junction capacitance C_(SL) of the PN junction between the source N⁺ layer 103 to which the source line is connected and the floating body 102, and the junction capacitance C_(BL) of the PN junction between the drain N⁺ layer 104 to which the bit line is connected and the floating body 102 and is expressed as follows.

C_(FB)=C_(WL)+C_(BL)+C_(SL)   (12)

The capacitive coupling ratio β_(WL) between the gate to which the word line is connected and the floating body is expressed as follows.

β_(WL)=C_(WL)/(C_(WL)+C_(BL)+CSL)   (13)

Therefore, a change in the word line voltage V_(WL) at the time of reading or writing affects the voltage of the floating body 102 that functions as a storage node (contact point) of the memory cell. This is illustrated in FIG. 8B. When the word line voltage V_(WL) rises from 0 V to V_(WHL) at the time of reading or writing, the voltage V_(FB) of the floating body 102 rises from V_(FB1), which is the voltage in the initial state before the word line voltage changes, to V_(FB2) due to capacitive coupling with the word line. The voltage change amount ΔV_(FB) is expressed as follows.

$\begin{matrix} {{\Delta V_{FB}} = {{V_{{FB}2} - V_{{FB}1}} = {\beta_{WL} \times V_{WLH}}}} & (14) \end{matrix}$

Here, for β_(WL) in expression (13), the contribution ratio of C_(WL)is large and, for example, C_(WL):C_(BL):C_(SL)=8:1:1 holds. This results in β_(WL)=0.8. When the word line changes, for example, from 5 V at the time of writing to 0 V after the end of writing, the floating body 102 receives an amplitude noise of 5 V×β_(WL)=4 V due to capacitive coupling between the word line WL and the floating body 102. Accordingly, a sufficient margin is not provided to the potential difference between the “1” potential and the “0” potential of the floating body 102 at the time of writing, which is a problem.

FIGS. 9A to 9C illustrate a read operation where FIG. 9A illustrates a “1” write state and FIG. 9B illustrates a “0” write state. In actuality, however, even when Vb is set for the floating body 102 to write “1”, once the word line returns to 0 V at the end of writing, the floating body 102 is lowered to a negative bias. When “0” is written, the floating body 102 is lowered to a further negative bias, and it is difficult to provide a sufficiently large margin to the potential difference between “1” and “0” at the time of writing as illustrated in FIG. 9C. Therefore, there has been difficulty in commercially introducing DRAM memory cells actually including no capacitor.

CITATION LIST Patent Literature

[PTL 1] Japanese Unexamined Patent Application Publication No. 2-188966

[PTL 2] Japanese Unexamined Patent Application Publication No. 3-171768

[PTL 3] Japanese Patent No. 3957774

Non Patent Literature

[NPL 1] Hiroshi Takato, Kazumasa Sunouchi, Naoko Okabe, Akihiro Nitayama, Katsuhiko Hieda, Fumio Horiguchi, and Fujio Masuoka: IEEE Transaction on Electron Devices, Vol. 38, No. 3, pp. 573-578 (1991)

[NPL 2] H. Chung, H. Kim, H. Kim, K. Kim, S. Kim, K. Dong, J. Kim, Y.C. Oh, Y. Hwang, H. Hong, G. Jin, and C. Chung: “4F2 DRAM Cell with Vertical Pillar Transistor (VPT)”, 2011 Proceeding of the European Solid-State Device Research Conference, (2011)

[NPL 3] H. S. Philip Wong, S. Raoux, S. Kim, Jiale Liang, J. R. Reifenberg, B. Rajendran, M. Asheghi and K. E. Goodson: “Phase Change Memory”, Proceeding of IEEE, Vol. 98, No. 12, December, pp. 2201-2227 (2010)

[NPL 4] T. Tsunoda, K. Kinoshita, H. Noshiro, Y. Yamazaki, T. Iizuka, Y. Ito, A. Takahashi, A. Okano, Y. Sato, T. Fukano, M. Aoki, and Y. Sugiyama : “Low Power and High Speed Switching of Ti-doped NiO ReRAM under the Unipolar Voltage Source of less than 3V”, IEDM (2007)

[NPL 5] W. Kang, L. Zhang, J. Klein, Y. Zhang, D. Ravelosona, and W. Zhao: “Reconfigurable Codesign of STT-MRAM Under Process Variations in Deeply Scaled Technology”, IEEE Transaction on Electron Devices, pp. 1-9 (2015)

[NPL 6] M. G. Ertosum, K. Lim, C. Park, J. Oh, P. Kirsch, and K. C. Saraswat: “Novel Capacitorless Single-Transistor Charge-Trap DRAM (1T CT DRAM) Utilizing Electron”, IEEE Electron Device Letter, Vol. 31, No. 5, pp. 405-407 (2010)

[NPL 7] J. Wan, L. Rojer, A. Zaslaysky, and S. Critoloveanu: “A Compact Capacitor-Less High-Speed DRAM Using Field Effect-Controlled Charge Regeneration”, Electron Device Letters, Vol. 35, No. 2, pp. 179-181 (2012)

[NPL 8] T. Ohsawa, K. Fujita, T. Higashi, Y. Iwata, T. Kajiyama, Y. Asao, and K. Sunouchi: “Memory design using a one-transistor gain cell on SOI”, IEEE JSSC, vol. 37, No. 11, pp. 1510-1522 (2002).

[NPL 9] T. Shino, N. Kusunoki, T. Higashi, T. Ohsawa, K. Fujita, K. Hatsuda, N. Ikumi, F. Matsuoka, Y. Kajitani, R. Fukuda, Y. Watanabe, Y. Minami, A. Sakamoto, J. Nishimura, H. Nakajima, M. Morikado, K. Inoh, T. Hamamoto, A. Nitayama: “Floating Body RAM Technology and its Scalability to 32 nm Node and Beyond”, IEEE IEDM (2006).

[NPL 10] E. Yoshida, T. Tanaka: “A Design of a Capacitorless 1T-DRAM Cell Using Gate-induced Drain Leakage (GIDL) Current for Low-power and High-speed Embedded Memory,” IEEE IEDM (2003).

[NPL 11] J. Y. Song, W. Y. Choi, J. H. Park, J. D. Lee, and B-G. Park: “Design Optimization of Gate-All-Around (GAA) MOSFETs”, IEEE Trans. Electron Devices, vol. 5, no. 3, pp. 186-191, May 2006.

[NPL 12] N. Loubet, et al.: “Stacked Nanosheet Gate-All-Around Transistor to Enable Scaling Beyond FinFET”, 2017 IEEE Symposium on VLSI Technology Digest of Technical Papers, T17-5, T230-T231, June 2017.

[NPL 13] H. Jiang, N. Xu, B. Chen, L. Zengl, Y. He, G. Du, X. Liu and X. Zhang: “Experimental investigation of self heating effect (SHE) in multiple-fin SOI FinFETs”, Semicond. Sci. Technol. 29 (2014) 115021 (7pp).

[NPL 14] E. Yoshida, and T. Tanaka: “A Capacitorless 1T-DRAM Technology Using Gate-Induced Drain-Leakage (GIDL) Current for Low-Power and High-Speed Embedded Memory”, IEEE Transactions on Electron Devices, Vol. 53, No. 4, pp. 692-697, Apr. 2006.

SUMMARY OF INVENTION Technical Problem

In capacitor-less single-transistor DRAMs (gain cells), capacitive coupling between the word line and the floating body is strong. When the potential of the word line is changed at the time of data reading or at the time of data writing, the change is transmitted as direct noise to the floating body, which is a problem. This causes a problem of erroneous reading or erroneous rewriting of storage data and makes it difficult to commercially introduce capacitor-less single-transistor DRAMs (gain cells).

Solution to Problem

To solve the above-described problem, a memory device according to the present invention is

a memory device including a plurality of pages arranged in a column direction, each of the pages being constituted by a plurality of memory cells arranged in a row direction on a substrate,

each memory cell included in each of the pages including:

a semiconductor base material that stands on the substrate in a vertical direction or that extends along the substrate in a horizontal direction;

a first impurity layer and a second impurity layer that are disposed at respective ends of the semiconductor base material;

a first gate insulating layer that partially or entirely surrounds a side surface of the semiconductor base material between the first impurity layer and the second impurity layer and that is in contact with or in close vicinity to the first impurity layer;

a second gate insulating layer that surrounds the side surface of the semiconductor base material, that is connected to the first gate insulating layer, and that is in contact with or in close vicinity to the second impurity layer;

a first gate conductor layer that partially or entirely covers the first gate insulating layer;

a second gate conductor layer that covers the second gate insulating layer; and

a channel semiconductor layer that is the semiconductor base material and that is covered by the first gate insulating layer and the second gate insulating layer, in which

voltages applied to the first gate conductor layer, the second gate conductor layer, the first impurity layer, and the second impurity layer are controlled to perform a page write operation and a page erase operation,

the first impurity layer of the memory cell is connected to a source line, the second impurity layer thereof is connected to a bit line, one of the first gate conductor layer or the second gate conductor layer thereof is connected to a word line, and the other of the first gate conductor layer or the second gate conductor layer thereof is connected to a driving control line,

the bit lines are connected to sense amplifier circuits with a switch circuit therebetween,

in a page read operation, page data in a group of memory cells selected by the word line is read to the sense amplifier circuits, and

in a page sum-of-products read operation, a voltage is applied to the driving control line such that memory cell currents, in the group of memory cells, flowing into the bit lines multiply N-fold (N is a positive integer) (first invention).

In the first invention described above, in the page sum-of-products read operation, at least two word lines are selected in multiple selection, a first voltage is applied to a first driving control line such that first memory cell currents, in a first group of memory cells, flowing into the bit lines multiply M-fold (M is a positive integer), a second voltage is applied to a second driving control line such that second memory cell currents, in a second group of memory cells, flowing into the bit lines multiply K-fold (K is a positive integer), and each of the first memory cell currents and a corresponding one of the second memory cell currents are added up for a corresponding one of the bit lines and read to a corresponding one of the sense amplifier circuits (second invention).

In the first invention described above, the sense amplifier circuits are forced-inversion-type sense amplifier circuits, and when a sum of memory cell currents added up for each of the bit lines is larger than a reference current, a corresponding one of the forced-inversion-type sense amplifier circuits is inverted (third invention).

In the third invention described above, in the page sum-of-products read operation, a sum total current of the memory cell currents obtained by sum-of-products calculation for each of the bit lines is read by a corresponding one of the forced-inversion-type sense amplifier circuits by the reference current that is smaller than the sum total current (fourth invention).

In the third invention described above, the reference current is decreased from a large current to a small current in stages, and the sum of the memory cell currents is read by the forced-inversion-type sense amplifier circuit (fifth invention).

In the first invention described above, the memory cell currents flowing into each of the bit lines in the page sum-of-products read operation is read to a corresponding one of the sense amplifier circuits, and a sum-of-products calculation result is stored in an N-bit (N is a positive integer) latch circuit (sixth invention).

In the first invention described above, a first gate capacitance between the first gate conductor layer and the channel semiconductor layer is larger than a second gate capacitance between the second gate conductor layer and the channel semiconductor layer (seventh invention).

In the first invention described above, the first gate conductor layer is isolated into at least two conductor layers around the first gate insulating layer when viewed in an axial direction of the semiconductor base material (eighth invention).

In the first invention described above, in the page write operation, a group of positive holes generated by an impact ionization phenomenon are retained inside the channel semiconductor layer, and a voltage of the channel semiconductor layer is made equal to a first data retention voltage that is higher than the voltage of either the first impurity layer or the second impurity layer or that is higher than the voltages of both the first impurity layer and the second impurity layer, and in the page erase operation, the voltages applied to the first impurity layer, the second impurity layer, the first gate conductor layer, and the second gate conductor layer are controlled to discharge the group of positive holes through either the first impurity layer or the second impurity layer or both the first impurity layer and the second impurity layer, and the voltage of the channel semiconductor layer is made equal to a second data retention voltage that is lower than the first data retention voltage (ninth invention).

BRIEF DESCRIPTION OF DRAWINGS

FIG. 1 is a structural diagram of an SGT-including memory device according to a first embodiment.

FIGS. 2A, 2B and 2C include diagrams for explaining an effect attained in a case where the gate capacitance of a first gate conductor layer 5 a connected to a plate line PL is made larger than the gate capacitance of a second gate conductor layer 5 b to which a word line WL is connected in the SGT-including memory device according to the first embodiment.

FIGS. 3AA, 3AB and 3AC include diagrams for explaining a mechanism of a write operation of the SGT-including memory device according to the first embodiment.

FIG. 3B includes diagrams for explaining the mechanism of the write operation of the SGT-including memory device according to the first embodiment.

FIG. 4A is a diagram for explaining a mechanism of a page erase operation of the SGT-including memory device according to the first embodiment.

FIGS. 4BA, 4BB, 4BC and 4BD include diagrams for explaining the mechanism of the page erase operation of the SGT-including memory device according to the first embodiment.

FIG. 4C includes diagrams for explaining the mechanism of the page erase operation of the SGT-including memory device according to the first embodiment.

FIGS. 4DA, 4DB, 4DC and 4DD include diagrams for explaining a mechanism of the page erase operation of the SGT-including memory device according to the first embodiment.

FIGS. 4EA, 4EB, 4EC and 4ED include diagrams for explaining a mechanism of the page erase operation of the SGT-including memory device according to the first embodiment.

FIGS. 5A, 5B and 5C include diagrams for explaining a mechanism of a read operation of the SGT-including memory device according to the first embodiment.

FIGS. 6AA and 6AB include diagrams for explaining a page sum-of-products read operation of the SGT-including memory device according to the first embodiment.

FIG. 6B is a circuit block diagram for explaining the page sum-of-products read operation of the SGT-including memory device according to the first embodiment.

FIG. 6C is a circuit block diagram for explaining the page sum-of-products read operation of the SGT-including memory device according to the first embodiment.

FIG. 6D is a circuit block diagram for explaining the page sum-of-products read operation of the SGT-including memory device according to the first embodiment.

FIGS. 7A, 7B, 7C and 7D include diagrams for explaining a write operation of a DRAM memory cell including no capacitor in the related art.

FIGS. 8A and 8B include diagrams for explaining a problem in the operation of the DRAM memory cell including no capacitor in the related art.

FIG. 9A, 9B and 9C include diagrams for explaining a read operation of the DRAM memory cell including no capacitor in the related art.

DESCRIPTION OF EMBODIMENTS

Hereinafter, embodiments of a semiconductor-element-including memory device (hereinafter called a dynamic flash memory) according to the present invention will be described with reference to the drawings.

First Embodiment

The structure and operation mechanisms of a dynamic flash memory cell according to a first embodiment of the present invention will be described with reference to FIG. 1 to FIGS. 5A-5C. The structure of the dynamic flash memory cell will be described with reference to FIG. 1. An effect attained in a case where the gate capacitance of a first gate conductor layer 5 a connected to a plate line PL is made larger than the gate capacitance of a second gate conductor layer 5 b to which a word line WL is connected will be described with reference to FIG. 2. A mechanism of a data write operation will be described with reference to FIGS. 3AA-3AC and FIG. 3B, mechanisms of a data erase operation will be described with reference to FIG. 4A to FIGS. 4EA-4ED, and a mechanism of a data read operation will be described with reference to FIGS. 5A to 5C.

FIG. 1 illustrates the structure of the dynamic flash memory cell according to the first embodiment of the present invention. On the top and the bottom of a silicon semiconductor pillar 2 (hereinafter, the silicon semiconductor pillar is referred to as “Si pillar”) (which is an example of “semiconductor base material” in the claims) of the P or i (intrinsic) conductivity type formed on a substrate, N⁺ layers 3 a and 3 b (which are examples of “first impurity layer” and “second impurity layer” in the claims), one of which functions as the source and the other functions as the drain, are formed respectively. The part of the Si pillar 2 between the N⁺ layers 3 a and 3 b that function as the source and the drain functions as a channel region 7 (which is an example of “channel semiconductor layer” in the claims). Around the channel region 7, a first gate insulating layer 4 a (which is an example of “first gate insulating layer” in the claims) and a second gate insulating layer 4 b (which is an example of “second gate insulating layer” in the claims) are formed. The first gate insulating layer 4 a and the second gate insulating layer 4 b are in contact with or in close vicinity to the N⁺ layers 3 a and 3 b that function as the source and the drain respectively. Around the first gate insulating layer 4 a and the second gate insulating layer 4 b, the first gate conductor layer 5 a (which is an example of “first gate conductor layer” in the claims) and the second gate conductor layer 5 b (which is an example of “second gate conductor layer” in the claims) are formed respectively. The first gate conductor layer 5 a and the second gate conductor layer 5 b are isolated from each other by an insulating layer 6 (which is also referred to as “first insulating layer”). The channel region 7 between the N⁺ layers 3 a and 3 b is constituted by a first channel Si layer 7 a (which is also referred to as “first channel semiconductor layer”) surrounded by the first gate insulating layer 4 a and a second channel Si layer 7 b (which is also referred to as “second channel semiconductor layer”) surrounded by the second gate insulating layer 4 b. Accordingly, the N⁺ layers 3 a and 3 b that function as the source and the drain, the channel region 7, the first gate insulating layer 4 a, the second gate insulating layer 4 b, the first gate conductor layer 5 a, and the second gate conductor layer 5 b constitute a dynamic flash memory cell 10. The N⁺ layer 3 a that functions as the source is connected to a source line SL (which is an example of “source line” in the claims), the N⁺ layer 3 b that functions as the drain is connected to a bit line BL (which is an example of “bit line” in the claims), the first gate conductor layer 5 a is connected to the plate line PL (which is an example of “driving control line” in the claims), and the second gate conductor layer 5 b is connected to the word line WL (which is an example of “word line” in the claims). Desirably, the structure is such that the gate capacitance of the first gate conductor layer 5 a to which the plate line PL is connected is larger than the gate capacitance of the second gate conductor layer 5 b to which the word line WL is connected.

In FIG. 1, to make the gate capacitance of the first gate conductor layer 5 a connected to the plate line PL larger than the gate capacitance of the second gate conductor layer 5 b to which the word line WL is connected, the gate length of the first gate conductor layer 5 a is made longer than the gate length of the second gate conductor layer 5 b. Alternatively, instead of making the gate length of the first gate conductor layer 5 a longer than the gate length of the second gate conductor layer 5 b, the thicknesses of the respective gate insulating layers may be made different such that the thickness of the gate insulating film of the first gate insulating layer 4 a is thinner than the thickness of the gate insulating film of the second gate insulating layer 4 b. Alternatively, the dielectric constants of the materials of the respective gate insulating layers may be made different such that the dielectric constant of the gate insulating film of the first gate insulating layer 4 a is higher than the dielectric constant of the gate insulating film of the second gate insulating layer 4 b. The gate capacitance of the first gate conductor layer 5 a connected to the plate line PL may be made larger than the gate capacitance of the second gate conductor layer 5 b to which the word line WL is connected, by a combination of any of the lengths of the gate conductor layers 5 a and 5 b and the thicknesses and dielectric constants of the gate insulating layers 4 a and 4 b.

FIGS. 2A to 2C are diagrams for explaining an effect attained in a case where the gate capacitance of the first gate conductor layer 5 a connected to the plate line PL is made larger than the gate capacitance of the second gate conductor layer 5 b to which the word line WL is connected.

FIG. 2A is a simplified structural diagram of the dynamic flash memory cell according to the first embodiment of the present invention and illustrates only main parts. To the dynamic flash memory cell, the bit line BL, the word line WL, the plate line PL, and the source line SL are connected, and the potential state of the channel region 7 is determined by the voltage states of the lines.

FIG. 2B is a diagram for explaining the capacitance relationships of the respective lines. The capacitance C_(FB) of the channel region 7 is equal to the sum of the capacitance C_(WL)between the gate conductor layer 5 b to which the word line WL is connected and the channel region 7, the capacitance C_(PL) between the gate conductor layer 5 a to which the plate line PL is connected and the channel region 7, the junction capacitance C_(SL)of the PN junction between the source N⁺ layer 3 a to which the source line SL is connected and the channel region 7, and the junction capacitance C_(BL)of the PN junction between the drain N⁺ layer 3 b to which the bit line BL is connected and the channel region 7, and is expressed as follows.

C_(FB)=C_(WL)+C_(PL) 30 C_(BL)+C_(SL)   (1)

Therefore, the coupling ratio β_(WL) between the word line WL and the channel region 7, the coupling ratio β_(PL) between the plate line PL and the channel region 7, the coupling ratio β_(BL) between the bit line BL and the channel region 7, and the coupling ratio β_(SL), between the source line SL and the channel region 7 are expressed as follows.

β_(WL)=C_(WL)/(C_(WL)+C_(PL)+C_(BL)+C_(SL))   (2)

β_(PL)=C_(PL)/(C_(WL)+C_(PL)+C_(BL)+C_(SL))   (3)

β_(BL)−C_(BL)/(C_(WL)+C_(PL)+C_(BL)+C_(SL))   (4)

β_(SL)=C_(SL)/(C_(WL)+C_(PL)+C_(BL)+C_(SL))   (5)

Here, C_(PL)>C_(WL) holds, and therefore, this results in β_(PL)>β_(WL).

FIG. 2C is a diagram for explaining a change in the voltage V_(FB) of the channel region 7 when the voltage V_(WL) of the word line WL rises at the time of a read operation or a write operation and subsequently drops. Here, the potential difference ΔV_(FB) when the voltage V_(WL) of the word line WL rises from 0 V to a high voltage state V_(WLH) and the voltage V_(FB) of the channel region 7 transitions from a low voltage state V_(FBL) to a high voltage state V_(FBH) is expressed as follows.

$\begin{matrix} {{\Delta V_{FB}} = {{V_{FBH} - V_{FBL}} = {\beta_{WL} \times V_{WLH}}}} & (6) \end{matrix}$

The coupling ratio β_(WL) between the word line WL and the channel region 7 is small and the coupling ratio β_(PL) between the plate line PL and the channel region 7 is large, and therefore, ΔV_(FB) is small, and the voltage V_(FB) of the channel region 7 negligibly changes even when the voltage V_(WL) of the word line WL changes at the time of a read operation or a write operation.

FIGS. 3AA to 3AC and FIG. 3B illustrate a memory write operation (which is an example of “page write operation” in the claims) of the dynamic flash memory cell according to the first embodiment of the present invention. FIG. 3AA illustrates a mechanism of the write operation, and FIG. 3AB illustrates operation waveforms of the bit line BL, the source line SL, the plate line PL, the word line WL, and the channel region 7 that functions as a floating body FB. At time T0, the dynamic flash memory cell is in a “0” erase state, and the voltage of the channel region 7 is equal to V_(FB)“0”. Vss is applied to the bit line BL, the source line SL, and the word line WL, and V_(PLL) is applied to the plate line PL. Here, for example, Vss is equal to 0 V and V_(PLL) is equal to 2 V. Subsequently, from time T1 to time T2, when the bit line BL rises from Vss to V_(BLH), in a case where, for example, Vss is equal to 0 V, the voltage of the channel region 7 becomes equal to V_(FB)“0”+β_(BL)×V_(BLH) due to capacitive coupling between the bit line BL and the channel region 7.

The description of the write operation of the dynamic flash memory cell will be continued with reference to FIGS. 3AA and 3AB. From time T3 to time T4, the word line WL rises from Vss to V_(WLH). Accordingly, when the threshold voltage for “0” erase for a second N-channel MOS transistor region that is a region in which the second gate conductor layer 5 b to which the word line WL is connected surrounds the channel region 7 is denoted by Vt_(WL)“0”, as the voltage of the word line WL rises, in a range from Vss to Vt_(WL)“0”, the voltage of the channel region 7 becomes equal to V_(FB)“0”+β_(BL)×V_(BLH)+β_(WL)×Vt_(WL)“0” due to second capacitive coupling between the word line WL and the channel region 7. When the voltage of the word line WL rises to Vt_(WL“)0” or above, an inversion layer 12 b in a ring form is formed in the channel region 7 on the inner periphery of the second gate conductor layer 5 b and interrupts the second capacitive coupling between the word line WL and the channel region 7.

The description of the write operation of the dynamic flash memory cell will be continued with reference to FIGS. 3AA and 3AB. From time T3 to time T4, for example, a fixed voltage V_(PLL)=2 V is applied to the first gate conductor layer 5 a to which the plate line PL is connected, and the second gate conductor layer 5 b to which the word line WL is connected is increased to, for example, V_(WLH)=4 V. As a result, as illustrated in FIG. 3AA, an inversion layer 12 a in a ring form is formed in the channel region 7 on the inner periphery of the first gate conductor layer 5 a to which the plate line PL is connected, and a pinch-off point 13 is present in the inversion layer 12 a. As a result, a first N-channel MOS transistor region including the first gate conductor layer 5 a operates in the saturation region. In contrast, the second N-channel MOS transistor region including the second gate conductor layer 5 b to which the word line WL is connected operates in the linear region. As a result, a pinch-off point is not present in the channel region 7 on the inner periphery of the second gate conductor layer 5 b to which the word line WL is connected, and the inversion layer 12 b is formed on the entire inner periphery of the gate conductor layer 5 b. The inversion layer 12 b that is formed on the entire inner periphery of the second gate conductor layer 5 b to which the word line WL is connected substantially functions as the drain of the second N-channel MOS transistor region including the second gate conductor layer 5 b. As a result, the electric field becomes maximum in a first boundary region of the channel region 7 between the first N-channel MOS transistor region including the first gate conductor layer 5 a and the second N-channel MOS transistor region including the second gate conductor layer 5 b that are connected in series, and an impact ionization phenomenon occurs in this region. This region is a source-side region when viewed from the second N-channel MOS transistor region including the second gate conductor layer 5 b to which the word line WL is connected, and therefore, this phenomenon is called a source-side impact ionization phenomenon. By this source-side impact ionization phenomenon, electrons flow from the N⁺ layer 3 a to which the source line SL is connected toward the N⁺ layer 3 b to which the bit line is connected. The accelerated electrons collide with lattice Si atoms, and electron-positive hole pairs are generated by the kinetic energy. Although some of the generated electrons flow into the first gate conductor layer 5 a and into the second gate conductor layer 5 b, most of the generated electrons flow into the N⁺ layer 3 b to which the bit line BL is connected (not illustrated).

As illustrated in FIG. 3AC, a generated group of positive holes 9 (which is an example of “group of positive holes” in the claims) are majority carriers in the channel region 7, with which the channel region 7 is charged to a positive bias. The N⁺ layer 3 a to which the source line SL is connected is at 0 V, and therefore, the channel region 7 is charged up to the built-in voltage Vb (about 0.7 V) of the PN junction between the N⁺ layer 3 a to which the source line SL is connected and the channel region 7. When the channel region 7 is charged to a positive bias, the threshold voltages for the first N-channel MOS transistor region and the second N-channel MOS transistor region decrease due to a substrate bias effect.

The description of the write operation of the dynamic flash memory cell will be continued with reference to FIG. 3AB. From time T6 to time T7, the voltage of the word line WL drops from V_(WLH) to Vss. During this period, although the second capacitive coupling is formed between the word line WL and the channel region 7, the inversion layer 12 b interrupts the second capacitive coupling until the voltage of the word line WL drops from V_(WLH) to a threshold voltage Vt_(WL)“1” for the second N-channel MOS transistor region or below when the voltage of the channel region 7 is equal to Vb. Therefore, the capacitive coupling between the word line WL and the channel region 7 is substantially formed only during a period from when the word line WL drops to Vt_(WL)“1” or below to when the word line WL drops to Vss. As a result, the voltage of the channel region 7 becomes equal to Vb−β_(WL)×Vt_(WL)“1”. Here, Vt_(WL)“1” is lower than Vt_(WL)“0” described above, and β_(WL)×Vt_(WL)“1” is small.

The description of the write operation of the dynamic flash memory cell will be continued with reference to FIG. 3AB. From time T8 to time T9, the bit line BL drops from V_(BLH) to Vss. The bit line BL and the channel region 7 are capacitively coupled with each other, and therefore, the “1” write voltage V_(FB)“1” of the channel region 7 becomes as follows at the end.

V_(FB)“1”=Vb−β_(WL)×Vt_(WL)“1”−β_(BL)×V_(BLH)   (7)

Here, the coupling ratio β_(BL) between the bit line BL and the channel region 7 is also small. Accordingly, as illustrated in FIG. 3B, the threshold voltage for the second N-channel MOS transistor region of the second channel region 7 b to which the word line WL is connected decreases. The memory write operation in which the voltage V_(FB)“1” in the “1” write state of the channel region 7 is assumed to be a first data retention voltage (which is an example of “first data retention voltage” in the claims) is performed to assign logical storage data “1”.

At the time of the write operation, electron-positive hole pairs may be generated by an impact ionization phenomenon in a second boundary region between the first impurity layer 3 a and the first channel semiconductor layer 7 a or in a third boundary region between the second impurity layer 3 b and the second channel semiconductor layer 7 b instead of the first boundary region, and the channel region 7 may be charged with the generated group of positive holes 9.

Note that the conditions of voltages applied to the bit line BL, the source line SL, the word line WL, and the plate line PL and the potential of the floating body described above are examples for performing the write operation, and other operation conditions based on which the write operation can be performed may be employed.

A mechanism of a memory erase operation (which is an example of “page erase operation” in the claims) will be described with reference to FIG. 4A to FIGS. 4EA-4ED.

FIG. 4A is a memory block circuit diagram for explaining a page erase operation. Although nine memory cells CL₁₁ to CL₃₃ in three rows and three columns are illustrated, the actual memory block is larger than this matrix. When memory cells are arranged in a matrix, one of the directions of the arrangement is called a row direction (or in rows) and the direction perpendicular to the one of the directions is called “column direction” (or in columns). To each of the memory cells, the source line SL, a corresponding one of the bit lines BL1 to BL23, a corresponding one of the plate lines PL₁ to PL_(3,) and a corresponding one of the word lines WL₁ to WL₃ are connected. For example, it is assumed that memory cells CL₂₁ to CL_(23,) in a certain page (which is an example of “page” in the claims), to which the plate line PL₂ and the word line WL₂ are connected are selected in this block and a page erase operation is performed.

A mechanism of the page erase operation will be described with reference to FIGS. 4BA to 4BD and FIG. 4C. Here, the channel region 7 between the N⁺ layers 3 a and 3 b is electrically isolated from the substrate and functions as a floating body. FIG. 4BA is a timing operation waveform diagram of main nodes in the erase operation. In FIG. 4BA, T0 to T12 indicate times from the start to the end of the erase operation. FIG. 4BB illustrates a state at time T0 before the erase operation, in which the group of positive holes 9 generated by impact ionization in the previous cycle are stored in the channel region 7. From time T1 to time T2, the bit lines BL1 to BL23 and the source line SL rise from Vss to V_(BLH) and V_(SLH) respectively and are in a high-voltage state. Here, Vss is, for example, equal to 0 V. With this operation, during the subsequent period from time T3 to time T4, the plate line PL₂ selected in the page erase operation rises from a first voltage V_(PLL) to a second voltage V_(PLH) and is in a high-voltage state, the word line WL₂ selected in the page erase operation rises from a third voltage Vss to a fourth voltage V_(WLH) and is in a high-voltage state, and this prevents the inversion layer 12 a on the inner periphery of the first gate conductor layer 5 a to which the plate line PL₂ is connected and the inversion layer 12 b on the inner periphery of the second gate conductor layer 5 b to which the word line WL₂ is connected from being formed in the channel region 7. Therefore, when the threshold voltage for the second N-channel MOS transistor region on the side of the word line WL₂ and the threshold voltage for the first N-channel MOS transistor region on the side of the plate line PL₂ are denoted by V_(tWL) and V_(tpL) respectively, it is desirable that the voltages V_(BLH) and V_(SLH) satisfy V_(BLH)>V_(WLH)+V_(tWL) and V_(SLH)>V_(PLH)+V_(tPL). For example, in a case where V_(tWL) and V_(tPL) are equal to 0.5 V, V_(WLH) and V_(PLH) need to be set to 3 V, and V_(BLH) and V_(SLH) need to be set to 3.5 V or higher.

The description of the mechanism of the page erase operation illustrated in FIG. 4BA will be continued. As the plate line PL₂ and the word line WL₂ respectively rise to the second voltage V_(PLH) and the fourth voltage V_(WLH) and are in a high-voltage state during a first period from time T3 to time T4, the voltage of the channel region 7 in a floating state is increased due to first capacitive coupling between the plate line PL₂ and the channel region 7 and the second capacitive coupling between the word line WL₂ and the channel region 7. The voltage of the channel region 7 rises from V_(FB)“1” in the “1” write state to a high voltage. This voltage rise is possible because the voltage of the bit lines BL1 to BL23 and that of the source line SL are high voltages of V_(BLH) and V_(SLH) respectively and the PN junction between the source N⁺ layer 3 a and the channel region 7 and the PN junction between the drain N⁺ layer 3 b and the channel region 7 are in a reverse bias state accordingly.

The description of the mechanism of the page erase operation illustrated in FIG. 4BA will be continued. During the subsequent period from time T5 to time T6, the voltage of the bit lines BL1 to BL23 and that of the source line SL respectively drop from high voltages of V_(BLH) and V_(SLH) to Vss. As a result, the PN junction between the source N⁺ layer 3 a and the channel region 7 and the PN junction between the drain N⁺ layer 3 b and the channel region 7 are in a forward bias state as illustrated in FIG. 4BC, and a remaining group of positive holes among the group of positive holes 9 in the channel region 7 are discharged to the source N⁺ layer 3 a and to the drain N⁺ layer 3 b. As a result, the voltage V_(FB) of the channel region 7 becomes equal to the built-in voltage Vb of the PN junction formed by the source N⁺ layer 3 a and the P layer, namely, the channel region 7, and the PN junction formed by the drain N⁺ layer 3 b and the P layer, namely, the channel region 7.

The description of the mechanism of the page erase operation illustrated in FIG. 4BA will be continued. Subsequently, from time T7 to time T8, the voltage of the bit lines BL1 to BL23 and that of the source line SL rise from Vss to high voltages of V_(BLH) and V_(SLH) respectively. With this operation, as illustrated in FIG. 4BD, when the plate line PL₂ drops from the second voltage V_(PLH) to the first voltage V_(PLL) and the word line WL₂ drops from the fourth voltage V_(WLH) to the third voltage Vss, from time T9 to time T10, the voltage VFB of the channel region 7 efficiently changes from Vb to V_(FB)“0” due to the first capacitive coupling between the plate line PL₂ and the channel region 7 and the second capacitive coupling between the word line WL₂ and the channel region 7 without the inversion layer 12 a on the side of the plate line PL₂ or the inversion layer 12 b on the side of the word line WL₂ being formed in the channel region 7. The voltage difference ΔV_(FB) of the channel region 7 between the “1” write state and the “0” erase state is expressed by the following expressions.

$\begin{matrix} {{V_{FB}{``1"}} = {{Vb} - {\beta_{WL} \times {Vt}_{WL}{``1"}} - {\beta_{BL} \times V_{BLH}}}} & (7) \end{matrix}$ $\begin{matrix} {{V_{FB}{``0"}} = {{Vb} - {\beta_{WL} \times V_{WLH}} - {\beta_{PL} \times \left( {V_{PLH} - V_{PLL}} \right)}}} & (8) \end{matrix}$ $\begin{matrix} {{\Delta V_{FB}} = {{{V_{FB}{``1"}} - {V_{FB}{``0"}}} = {{\beta_{WL} \times V_{WLH}} + {\beta_{PL} \times \left( {V_{PLH} - V_{PLL}} \right)} - {\beta_{WL} \times {Vt}_{WL}{``1"}} - {\beta_{BL} \times V_{BLH}}}}} & (9) \end{matrix}$

Here, the sum of β_(WL) and β_(PL) is greater than or equal to 0.8, ΔV_(FB) is large, and a sufficient margin is provided.

As a result, as illustrated in FIG. 4C, a large margin is provided between the “1” write state and the “0” erase state. Here, in the “0” erase state, the threshold voltage on the side of the plate line PL₂ is high due to a substrate bias effect. Therefore, when the voltage applied to the plate line PL₂ is set to, for example, the threshold voltage or lower, the first N-channel MOS transistor region on the side of the plate line PL₂ becomes non-conducting and does not allow the memory cell current to flow therethrough. This state is illustrated in the right part of FIG. 4C and indicated as “PL: non-conducting”.

The description of the mechanism of the page erase operation illustrated in FIG. 4BA will be continued. During the subsequent period, namely, a fourth period from time T11 to time T12, the voltage of the bit lines BL1 to BL23 drops from V_(BLH) to Vss and that of the source line SL drops from V_(SLH) to Vss, and the erase operation ends. At this time, although the bit lines BL1 to BL23 and the source line SL slightly decrease the voltage of the channel region 7 due to capacitive coupling, this decrease is equal to the increase in the voltage of the channel region 7 by the bit lines BL1 to BL23 and the source line SL due to capacitive coupling from time T7 to time T8, and therefore, the decrease and the increase in the voltage by the bit lines BL1 to BL23 and the source line SL are canceled out, and the voltage of the channel region 7 is not affected consequently. The page erase operation in which the voltage V_(FB)“0” in the “0” erase state of the channel region 7 is assumed to be a second data retention voltage (which is an example of “second data retention voltage” in the claims) is performed to assign logical storage data “0”. When the voltage applied to the first gate conductor layer 5 a connected to the plate line PL is set to a voltage higher than the threshold voltage at the time of logical storage data “1” and lower than the threshold voltage at the time of logical storage data “0” in data reading after the erase operation, a property that a current does not flow even when the voltage of the word line WL is increased can be attained as illustrated in FIG. 4C.

Now, a mechanism of the page erase operation will be described with reference to FIGS. 4DA to 4DD. FIGS. 4DA to 4DD are different from FIGS. 4BA to 4BD in that the bit lines BL1 to BL23 are kept at Vss or put in a floating state and the word line WL₂ is kept at Vss during the page erase operation. Accordingly, from time T1 to time T2, even when the source line SL rises from Vss to V_(SLH), the second N-channel MOS transistor region of the word line WL₂ is non-conducting, and the memory cell current does not flow therethrough. Therefore, the group of positive holes 9 caused by an impact ionization phenomenon are not generated. The others are the same as in FIGS. 4BA to 4BD, and the source line SL changes between Vss and V_(SLH), and the plate line PL₂ changes between V_(PLL) and V_(PLH). As a result, as illustrated in FIG. 4DC, the group of positive holes 9 are discharged to the first impurity layer, namely, the N⁺ layer 3 a, of the source line SL.

Now, a mechanism of the page erase operation will be described with reference to FIGS. 4EA to FIG. 4ED. FIGS. 4EA to 4ED are different from FIGS. 4BA to 4BD in that the source line SL is kept at Vss or put in a floating state and the plate line PL₂ is kept at Vss during the page erase operation. Accordingly, from time T1 to time T2, even when the bit lines BL1 to BL23 rise from Vss to VBLH, the first N-channel MOS transistor region of the plate line PL₂ is non-conducting, and the memory cell current does not flow therethrough. Therefore, the group of positive holes 9 caused by an impact ionization phenomenon are not generated. The others are the same as in FIGS. 4BA to 4BD, and the bit lines BL1 to BL23 change between Vss and V_(BLH), and the word line WL₂ changes between Vss and V_(WLH). As a result, as illustrated in FIG. 4EC, the group of positive holes 9 are discharged to the second impurity layer, namely, the N⁺ layer 3 b, of the bit lines BL1 to BL23.

Note that the conditions of voltages applied to the bit line BL, the source line SL, the word line WL, and the plate line PL and the potential of the floating body described above are examples for performing the page erase operation, and other operation conditions based on which the page erase operation can be performed may be employed.

FIGS. 5A to 5C are diagrams for explaining a read operation of the dynamic flash memory cell according to the first embodiment of the present invention. As illustrated in FIG. 5A, when the channel region 7 is charged up to the built-in voltage Vb (about 0.7 V), the threshold voltage for the second N-channel MOS transistor region including the second gate conductor layer 5 b to which the word line WL is connected decreases due to a substrate bias effect. This state is assigned to logical storage data “1”. As illustrated in FIG. 5B, a memory block selected before writing is in an erase state “0” in advance, and the voltage V_(FB) of the channel region 7 is equal to V_(FB)“0”. With a write operation, a write state “1” is stored at random. As a result, logical storage data of logical “0” and that of logical “1” are created for the word line WL. As illustrated in FIG. 5C, the level difference between the two threshold voltages of the word line WL is used to perform reading by a sense amplifier. When the voltage applied to the first gate conductor layer 5 a connected to the plate line PL is set to a voltage higher than the threshold voltage at the time of logical storage data “1” and lower than the threshold voltage at the time of logical storage data “0” in data reading, a property that a current does not flow even when the voltage of the word line WL is increased can be attained as illustrated in FIG. 5C.

Note that the conditions of voltages applied to the bit line BL, the source line SL, the word line WL, and the plate line PL and the potential of the floating body described above are examples for performing the read operation, and other operation conditions based on which the read operation can be performed may be employed.

With reference to FIGS. 6AA and 6AB to FIG. 6D, a page sum-of-products read operation (which is an example of “page sum-of-products read operation” in the claims) of the dynamic flash memory cell according to the first embodiment of the present invention will be described.

FIG. 6AA illustrates the memory cell current in the “1” write state and in the “0” erase state similar to that described with reference to FIG. 3B, FIG. 4C, and FIG. 5C and illustrates a state in which the memory cell current (which is an example of “memory cell current” in the claims) in the “1” write state is in saturation as the voltage of the word line WL is increased. The memory cell current in the “1” write state is controlled also by the plate line PL, and therefore, when the voltage of the plate line PL is fixed, the memory cell current in the “1” write state is limited and is in saturation as illustrated in FIG. 6AA.

Here, when the saturation current of the memory cell current illustrated in FIG. 6AA is denoted by Isat, Isat is expressed by expression (10).

Isat=½×β(Vg−Vth)²   (10)

In expression (10), Vg denotes the applied voltage of the plate line PL, Vth is a threshold voltage of the first gate conductor layer, and β is expressed by expression (11).

β=(μ×ϵ/t_(ox))×(W/L)   (11)

In expression (11), μ denotes mobility, δ denotes the dielectric constant of the oxide film, t_(ox) denotes the thickness of the oxide film, and W/L denotes the transistor size, where W denotes the channel width of the first gate conductor layer, and L denotes the channel length of the first gate conductor layer. In the structure illustrated in FIG. 1, the channel length is the length of the first channel region 7 a in the vertical direction, and the channel width is the circumferential length of the horizontal cross section of the first channel region 7 a.

FIG. 6AB illustrates a state in which the sum of products for memory cells in the “1” write state is calculated for the bit line. The voltage applied to the plate line PL is changed such that the saturation current of the memory cell current in the memory cell in the “1” write state multiplies N-fold. For example, a case where the saturation current when the applied voltage of the plate line PL is set to 1 V is equal to 1 μA and where the threshold voltage Vth of the first gate conductor layer is equal to 0.5 V will be described. To calculate applied voltages of the plate line PL for making the one-fold saturation current 1 μA multiply two-fold and three-fold to attain 2 μA and 3 μA, expression (10) can be used. Expression (10) shows Isat=½(Vg−Vth)², and therefore, when ½β is regarded as a constant, the term (Vg−Vth)² needs to multiply two-fold and three-fold. The case of one-fold results in (Vg−Vth)²=(1−0.5)²=0.25. Therefore, the case of two-fold results in 0.25×2 and the case of three-fold results in 0.25×3. Based on (Vg−Vth)²=0.25×2 and (Vg−Vth)²=0.25×3, the voltages Vg of the plate line PL in these cases are Vg=√0.5+0.5=1.2 V and Vg=√0.75+0.5=1.4 V. Therefore, when the applied voltage Vg of the plate line PL is increased form 1 V to 1.2 V and 1.4 V, the saturation current of the memory cell current increases from 1 μA to 2 μA and 3 μA, and this current is compared with a reference current (which is an example of “reference current” in the claims). When the reference current is decreased from a large current to a small current in stages, namely, for example, from 2.5 times, to 1.5 times and 0.5 times the saturation current of the memory cell current in the “1” write state, based on the product of the memory cell current in the “1” write state, determination concerning the case of summation for the memory cell in the “1” write state in four patterns, namely, “1”×3=11 (two bits in binary), “1”×2 =10, “1”×1=01, and “1”×0=00, can be performed.

The page sum-of-products read operation will be described with reference to the circuit diagram in FIG. 6B. The bit line BL is connected to a plurality of memory cells C1 to CM and is connected to a sense amplifier circuit (which is an example of “sense amplifier circuit” in the claims) SA with an N-type MOS transistor T4 that is a switch circuit (which is an example of “switch circuit” in the claims) therebetween. To the memory cells C1 to CM, word lines WL1 to WLM and plate lines PL1 to PLM are connected respectively. Although one memory cell C1 to one memory cell CM respectively connected to the word lines WL1 to WLM and to the plate lines PL1 to PLM are illustrated, in actuality, a plurality of groups of memory cells (which is an example of “group of memory cells” in the claims) selected by the word lines WL1 to WLM and the plate lines PL1 to PLM are present. When a certain word line WL is selected, page data (which is an example of “page data” in the claims) is read to the bit line BL.

In the circuit diagram in FIG. 6B, the sense amplifier circuit SA is a forced-inversion-type sense amplifier circuit (which is an example of “forced-inversion-type sense amplifier circuit” in the claims). The forced-inversion-type sense amplifier circuit is constituted by N-type MOS transistors T1, T1A, and T1B and P-type MOS transistors T2, T2A, and T2B. An N-type MOS transistor T3 having a gate to which a reference current control signal VREF is input is connected to a contact point NB from which the reference current flows, and the summated memory cell current flowing from a contact point NA is compared with each current magnitude.

For example, in a case of determining the summated quantity for the memory cell in the “1” write state among the memory cells summated for the bit line BL, as illustrated in FIG. 6AB, the summated quantity for the memory cell in the “1” write state multiplies three-fold at maximum. Therefore, as the reference current, the medium current between a current two times the saturation current of the memory cell in the “1” write state and a current three times the saturation current of the memory cell in the “1” write state needs to be selected as an initial reference current. When the node NA drops from “high” to “low”, the memory cell current summated for the bit line BL is found to be equal to three times the saturation current in the “1” write state. This result is stored in an N-bit latch circuit (which is an example of “N-bit latch circuit” in the claims) Nb_LAT.

Next, the medium current between a current one time the saturation current of the memory cell in the “1” write state and a current two times the saturation current of the memory cell in the “1” write state is selected as the reference current. In this case, when the node NA drops from “high” to “low”, the memory cell current summated for the bit line BL is found to be equal to two times the saturation current in the “1” write state. Note that determination concerning the case of three times the memory cell current in the “1” write state for the same bit line BL has already been performed as described above, and therefore, the node NA of the forced-inversion-type sense amplifier circuit SA is kept in a “low” state. When the value of the reference current is thus decreased from a large current to a small current in stages, the memory cell from which reading to the bit line BL is performed is summated in a state of multiplication by what times can be determined, and the result can be stored in the latch circuit Nb_LAT.

In FIG. 6B, storage data in the latch circuit Nb_LAT is read to input/output lines IO and /IO via N-type MOS transistors T6A and T6B. A P-type MOS transistor T5 has a gate to which a bit line pre-charge signal is input to pre-charge the bit line BL. To the N-type MOS transistor T4, a transfer signal FT is input.

With reference to FIG. 6C and FIG. 6D, an example in which the sum of products of a plurality of sets of page data is calculated for each of the bit lines BL0 to BL2 will be described.

In FIG. 6C, memory cells C00 to C32 in three rows and four columns constitute a part of a block. Although the memory cells C00 to C32 in three rows and four columns are illustrated here, memory cells in a matrix larger than three rows and four columns constitute the actual block. To each of the memory cells, a corresponding one of the word lines WL0 to WL2, a corresponding one of the plate lines PL0 to PL2, the source line SL, and a corresponding one of the bit lines BL0 to BL3 are connected. Transistors T40 to T43 each having a gate to which the transfer signal FT is input constitute the switch circuit. The drains of transistors T50 to T53 each having a gate connected to the bit line pre-charge signal FP are connected to a bit line pre-charge voltage VP, and the sources thereof are connected to the bit lines BL0 to BL3 respectively. The bit lines BL0 to BL3 are respectively connected to forced-inversion-type sense amplifier circuits SA0 to SA3 with the switch circuit constituted by T40 to T43 therebetween. The forced-inversion-type sense amplifier circuits SA0 to SA3 are connected to the pair of complementary input/output lines IO and/IO, with transistors T6A0 to T6B3 each having a gate connected to a corresponding one of the column selection lines CSL0 to CSL3 therebetween. To the forced-inversion-type sense amplifier circuits SA0 to SA3, N-bit latch circuits Nb_LAT0 to Nb_LAT3 are connected respectively, in which the results of determination, by the forced-inversion-type sense amplifier circuits SA0 to SA3, of the memory cell currents for which the sums of products are respectively calculated for the bit lines BL0 to BL3 are stored.

FIG. 6D illustrates a state in which “1” is written to memory cells among the memory cells C00 to C32 at random and the group of positive holes 9 are stored in the channel semiconductor layer 7 of each of the memory cells. FIG. 6D assumes a case where, for example, a memory cell C10 is a memory cell in the “1” write state in a first group of memory cells (which is an example of “first group of memory cells” in the claims) C00 to C30 connected to the word line WL0, memory cells C01, C11, and C31 are memory cells in the “1” write state in a second group of memory cells (which is an example of “second group of memory cells” in the claims) C01 to C31 connected to the word line WL1, and memory cells C02 and C12 are memory cells in the “1” write state in a third group of memory cells C02 to C32 connected to the word line WL2. Here, the three word lines WL0 to WL2 are simultaneously selected in multiple selection. To the plate line PL0 that is a first driving control line (which is an example of “first driving control line” in the claims), a first voltage (which is an example of “first voltage” in the claims) is applied. To the plate line PL₁ that is a second driving control line (which is an example of “second driving control line” in the claims), a second voltage (which is an example of “second voltage” in the claims) is applied. To the plate line PL2 that is a third driving control line, a third voltage is applied. The multiple selection can be easily made by providing an address latch circuit in a row decoder circuit (not illustrated).

In FIG. 6D, the first voltage is set for the plate line PL0 such that the saturation currents of the memory cell currents in the first group of memory cells multiply one-fold, the second voltage is set for the plate line PL1 such that the saturation currents of the memory cell currents in the second group of memory cells multiply two-fold, and the third voltage is set for the plate line PL2 such that the saturation currents of the memory cell currents in the third group of memory cells multiply three-fold. As a result, into each of the bit lines BL0 to BL3, the sum total current (which is an example of “sum total current” in the claims) of the three memory cells flows. Specifically, reading from C00, C01, and C02 to the bit line BL0 is performed, reading from C10, C11, and C12 to the bit line BL1 is performed, reading from C20, C21, and C22 to the bit line BL22 is performed, and reading from C30, C31, and C32 to the bit line BL23 is performed.

In FIG. 6D, three sets of page data are (C00=0×1, C10=1×1, C20=0×1, and C30=0×1), (C01=1×2, C11=1×2, C21=0×2, and C31=1×2), and (C02=1×3, C12=1×3, C22=0×3, and C32=0×3). For each of the bit lines BL0 to BL3, the sum of products of the sets of page data is calculated. Specifically, the results are BL0=C00+C01+C02=5, BL1=C10+C11+C12=6, BL2=C20+C21+C22=0, and BL3=C30+C31+C32=2.

The results for the bit lines BL0 to BL23 are determined by the forced-inversion-type sense amplifier circuit SA0 to SA3, and the results are stored in the N-bit latch circuits Nb_LATO to Nb_LAT3. This case results in Nb_LAT0=101 (binary), Nb_LAT1=110, Nb_LAT2=000, and Nb_LAT3=010. These results are read to the input/output lines IO and/IO via the MOS transistors T6A0 to T6B3.

Accordingly, the sum of products of sets of page data in the groups of memory cells selected by the word lines WL0 to WL2 in multiple selection is calculated for each of the bit lines BL0 to BL23, and determination is easily performed by the forced-inversion-type sense amplifier circuits SA0 to SA3. Accordingly, sum-of-products data of a plurality of sets of page data can be calculated without reading the plurality of sets of page data outside the dynamic flash memory device. As a result, power consumption can be significantly reduced, and a significantly increased calculation speed can be attained. Therefore, in the AI field, an optimum memory device can be provided.

Although the page sum-of-products read operation has been described above with reference to the saturation region of the memory cell current, the page sum-of-products read operation may be performed by using the memory cell current in the linear region in which the voltage of the word line WL is low. In this case, the reference current is also controlled in accordance with the memory cell current.

Regardless of whether the horizontal cross-sectional shape of the Si pillar 2 illustrated in FIG. 1 is a round shape, an elliptic shape, or a rectangular shape, the operations of the dynamic flash memory described in this embodiment can be performed. Further, a dynamic flash memory cell having a round shape, a dynamic flash memory cell having an elliptic shape, and a dynamic flash memory cell having a rectangular shape may coexist on the same chip.

With reference to FIG. 1, the dynamic flash memory element including, for example, an SGT in which the first gate insulating layer 4 a and the second gate insulating layer 4 b that surround the entire side surface of the Si pillar 2 standing on the substrate in the vertical direction are provided and which includes the first gate conductor layer 5 a and the second gate conductor layer 5 b that entirely surround the first gate insulating layer 4 a and the second gate insulating layer 4 b has been described. As illustrated in the description of this embodiment, the dynamic flash memory element needs to have a structure that satisfies the condition that the group of positive holes 9 generated by an impact ionization phenomenon are retained in the channel region 7. For this, the channel region 7 needs to have a floating body structure isolated from the substrate. Accordingly, even when the semiconductor base material of the channel region is formed horizontally along the substrate by using, for example, GAA (Gate All Around, see, for example, NPL 11) technology, which is one type of SGT, or nanosheet technology (see, for example, NPL 12), the above-described operations of the dynamic flash memory can be performed. Alternatively, the dynamic flash memory element may have a device structure using SOI (Silicon On Insulator) (see, for example, NPL 7 to NPL 10). In this device structure, the bottom portion of the channel region is in contact with an insulating layer of the SOI substrate, and the other portion of the channel region is surrounded by a gate insulating layer and an element isolation insulating layer. Also with such a structure, the channel region has a floating body structure. Accordingly, the dynamic flash memory element provided in this embodiment needs to satisfy the condition that the channel region has a floating body structure. Even with a structure in which a Fin transistor (see, for example, NPL 13) is formed on an SOI substrate, when the channel region has a floating body structure, the dynamic flash operations can be performed.

To write “1”, electron-positive hole pairs may be generated by using a gate-induced drain leakage (GIDL) current (see for example, NPL 14), and the channel region 7 may be filled with the generated group of positive holes.

Expressions (1) to (14) provided in the specification and in the drawings are expressions used to qualitatively explain the phenomena, and are not intended to limit the phenomena.

Although the reset voltages of the word line WL, the bit line BL, and the source line SL are specified as Vss in the explanations of FIGS. 3AA-3AC and FIG. 3B, the reset voltages may be set to different voltages.

Although FIGS. 4BA-4BD, FIGS. 4DA-4DD, and FIGS. 4EA-4ED and the description thereof illustrate example conditions of the page erase operation, the voltages applied to the source line SL, the plate line PL, the bit line BL, and the word line WL may be changed as long as a state in which the group of positive holes 9 in the channel region 7 are discharged through either the N⁺ layer 3 a or the N⁺ layer 3 b or both the N⁺ layer 3 a and the N⁺ layer 3 b can be attained. Further, in the page erase operation, a voltage may be applied to the source line SL of a selected page, and the bit line BL may be put in a floating state. In the page erase operation, a voltage may be applied to the bit line BL of a selected page, and the source line SL may be put in a floating state.

In FIG. 1, in the vertical direction, in a part of the channel region 7 surrounded by the insulating layer 6 that is the first insulating layer, the potential distribution of the first channel region 7 a and that of the second channel region 7 b are connected and formed. Accordingly, the first channel region 7 a and the second channel region 7 b that constitute the channel region 7 are connected in the vertical direction in the region surrounded by the insulating layer 6 that is the first insulating layer.

Note that in FIG. 1, it is desirable to make the length of the first gate conductor layer 5 a, in the vertical direction, to which the plate line PL is connected further longer than the length of the second gate conductor layer 5 b, in the vertical direction, to which the word line WL is connected to attain C_(PL)>C_(WL). However, when only the plate line PL is added, the coupling ratio (C_(WL)/(C_(PL)+C_(WL)+C_(BL)+C_(sL))), of capacitive coupling, of the word line WL to the channel region 7 decreases. As a result, the potential change ΔV_(FB) of the floating body, namely, the channel region 7, decreases.

As the voltage V_(PLL) of the plate line PL, a fixed voltage of, for example, about 1 V may be applied.

Note that in the specification and the claims, the meaning of “cover” in a case of “for example, a gate insulating layer or a gate conductor layer covers, for example, a channel” also includes a case of surrounding entirely as in an SGT or GAA, a case of surrounding except a portion as in a Fin transistor, and a case of overlapping a flat object as in a planar transistor.

Although the first gate conductor layer 5 a entirely surrounds the first gate insulating layer 4 a in FIG. 1, a structure may be employed in which the first gate conductor layer 5 a partially surrounds the first gate insulating layer 4 a in plan view. The first gate conductor layer 5 a may be divided into at least two gate conductor layers and each of which may be operated as a plate line PL electrode. Similarly, the second gate conductor layer 5 b may be divided into two or more gate conductor layers, and the gate conductor layers may each function as a conductive electrode of the word line and may be operated synchronously or asynchronously. Accordingly, the operations of the dynamic flash memory can be performed.

Although the page sum-of-products read operation of a one-bit dynamic flash memory cell constituted by a single semiconductor base material has been described with reference to FIGS. 6AA to FIG. 6D, the present invention is also effective to the operation modes of a one-bit high-speed dynamic flash memory cell constituted by two semiconductor base materials that store complementary data of “1” and “0”.

In FIG. 1, the first gate conductor layer 5 a may be connected to the word line WL, and the second gate conductor layer 5 b may be connected to the plate line PL. Also in this case, the operations of the dynamic flash memory described above can be performed.

The above-described conditions of voltages applied to the bit line BL, the source line SL, the word line WL, and the plate line PL and the voltage of the floating body are examples for performing basic operations including the erase operation, the write operation, and the read operation, and other voltage conditions may be employed as long as basic operations of the present invention can be performed.

This embodiment has the following features.

(Feature 1)

The dynamic flash memory cell of this embodiment is constituted by the N⁺ layers 3 a and 3 b that function as the source and the drain, the channel region 7, the first gate insulating layer 4 a, the second gate insulating layer 4 b, the first gate conductor layer 5 a, and the second gate conductor layer 5 b, which are formed in a pillar form as a whole. The N⁺ layer 3 a that functions as the source is connected to the source line SL, the N^(+ layer 3) b that functions as the drain is connected to the bit line BL, the first gate conductor layer 5 a is connected to the plate line PL, and the second gate conductor layer 5 b is connected to the word line WL. A structure is employed in which the gate capacitance of the first gate conductor layer 5 a to which the plate line PL is connected is larger than the gate capacitance of the second gate conductor layer 5 b to which the word line WL is connected, which is a feature. In the dynamic flash memory cell, the first gate conductor layer and the second gate conductor layer are stacked in the vertical direction. Accordingly, even when the structure is employed in which the gate capacitance of the first gate conductor layer 5 a to which the plate line PL is connected is larger than the gate capacitance of the second gate conductor layer 5 b to which the word line WL is connected, the memory cell area does not increase in plan view. Accordingly, a high-performance and highly integrated dynamic flash memory cell can be implemented.

(Feature 2)

With the page sum-of-products read operation of the dynamic flash memory cell according to the first embodiment of the present invention, sum-of-products data of a plurality of sets of page data can be calculated without reading the plurality of sets of page data outside the dynamic flash memory device. As a result, power consumption can be significantly reduced, and a significantly increased calculation speed can be attained. That is, a significant contribution can be made to the development of CIM (Computation-In Memory) technology for computation inside a memory device. Accordingly, in the AI field, an optimum memory device can be provided, system flexibility can be significantly increased, and a high-speed system can be attained.

(Feature 3)

In terms of the roles of the first gate conductor layer 5 a to which the plate line PL is connected in the dynamic flash memory cell according to the first embodiment of the present invention, in the write operation and in the read operation performed by the dynamic flash memory cell, the voltage of the word line WL changes. At this time, the plate line PL assumes the role of decreasing the capacitive coupling ratio between the word line WL and the channel region 7. As a result, an effect on changes in the voltage of the channel region 7 when the voltage of the word line WL changes can be substantially suppressed. Accordingly, the difference between the threshold voltages for the transistor regions of the word line WL indicating logical “0” and logical “1” can be increased. This leads to an increased operation margin of the dynamic flash memory cell.

Other Embodiments

Although the Si pillar is formed in the present invention, the Si pillar may be a semiconductor pillar made of a semiconductor material other than Si. This is similarly applicable to other embodiments according to the present invention.

To write “1”, electron-positive hole pairs may be generated by an impact ionization phenomenon using a gate-induced drain leakage (GIDL) current described in NPL 10 and NPL 14, and the floating body FB may be filled with the generated group of positive holes. This is similarly applicable to other embodiments according to the present invention.

Even with a structure in which the conductivity type that is the polarity of each of the N⁺ layers 3 a and 3 b and the P-layer Si pillar 2 in FIG. 1 is reversed, the operations of the dynamic flash memory can be performed. In this case, in the Si pillar 2 that is of N-type, the majority carriers are electrons. Therefore, a group of electrons generated by impact ionization are stored in the channel region 7, and a “1” state is set.

Various embodiments and modifications can be made to the present invention without departing from the spirit and scope of the present invention in a broad sense. The above-described embodiments are intended to explain examples of the present invention and are not intended to limit the scope of the present invention. Any of the above-described embodiments and modifications can be combined. Further, the above-described embodiments from which some of the constituent requirements are removed as needed are also within the scope of the technical spirit of the present invention.

INDUSTRIAL APPLICABILITY

With the semiconductor-element-including memory device according to the present invention, a high-density and high-performance dynamic flash memory that is an SGT-including memory device can be obtained. 

Listing of the claims:
 1. A semiconductor-element-including memory device, the memory device comprising a plurality of pages arranged in a column direction, each of the pages being constituted by a plurality of memory cells arranged in a row direction on a substrate, each memory cell included in each of the pages comprising: a semiconductor base material that stands on the substrate in a vertical direction or that extends along the substrate in a horizontal direction; a first impurity layer and a second impurity layer that are disposed at respective ends of the semiconductor base material; a first gate insulating layer that partially or entirely surrounds a side surface of the semiconductor base material between the first impurity layer and the second impurity layer and that is in contact with or in close vicinity to the first impurity layer; a second gate insulating layer that surrounds the side surface of the semiconductor base material, that is connected to the first gate insulating layer, and that is in contact with or in close vicinity to the second impurity layer; a first gate conductor layer that partially or entirely covers the first gate insulating layer; a second gate conductor layer that covers the second gate insulating layer; and a channel semiconductor layer that is the semiconductor base material and that is covered by the first gate insulating layer and the second gate insulating layer, wherein voltages applied to the first gate conductor layer, the second gate conductor layer, the first impurity layer, and the second impurity layer are controlled to perform a page write operation and a page erase operation, the first impurity layer of the memory cell is connected to a source line, the second impurity layer thereof is connected to a bit line, one of the first gate conductor layer or the second gate conductor layer thereof is connected to a word line, and the other of the first gate conductor layer or the second gate conductor layer thereof is connected to a driving control line, the bit lines are connected to sense amplifier circuits with a switch circuit therebetween, in a page read operation, page data in a group of memory cells selected by the word line is read to the sense amplifier circuits, and in a page sum-of-products read operation, a voltage is applied to the driving control line such that memory cell currents, in the group of memory cells, flowing into the bit lines multiply N-fold (N is a positive integer).
 2. The semiconductor-element-including memory device according to claim 1, wherein in the page sum-of-products read operation, at least two word lines are selected in multiple selection, a first voltage is applied to a first driving control line such that first memory cell currents, in a first group of memory cells, flowing into the bit lines multiply M-fold (M is a positive integer), a second voltage is applied to a second driving control line such that second memory cell currents, in a second group of memory cells, flowing into the bit lines multiply K-fold (K is a positive integer), and each of the first memory cell currents and a corresponding one of the second memory cell currents are added up for a corresponding one of the bit lines and read to a corresponding one of the sense amplifier circuits.
 3. The semiconductor-element-including memory device according to claim 1, wherein the sense amplifier circuits are forced-inversion-type sense amplifier circuits, and when a sum of memory cell currents added up for each of the bit lines is larger than a reference current, a corresponding one of the forced-inversion-type sense amplifier circuits is inverted.
 4. The semiconductor-element-including memory device according to claim 3, wherein in the page sum-of-products read operation, a sum total current of the memory cell currents obtained by sum-of-products calculation for each of the bit lines is read by a corresponding one of the forced-inversion-type sense amplifier circuits by the reference current that is smaller than the sum total current.
 5. The semiconductor-element-including memory device according to claim 3, wherein the reference current is decreased from a large current to a small current in stages, and the sum of the memory cell currents is read by the forced-inversion-type sense amplifier circuit.
 6. The semiconductor-element-including memory device according to claim 1, wherein the memory cell currents flowing into each of the bit lines in the page sum-of-products read operation is read to a corresponding one of the sense amplifier circuits, and a sum-of-products calculation result is stored in an N-bit (N is a positive integer) latch circuit.
 7. The semiconductor-element-including memory device according to claim 1, wherein a first gate capacitance between the first gate conductor layer and the channel semiconductor layer is larger than a second gate capacitance between the second gate conductor layer and the channel semiconductor layer.
 8. The semiconductor-element-including memory device according to claim 1, wherein the first gate conductor layer is isolated into at least two conductor layers around the first gate insulating layer when viewed in an axial direction of the semiconductor base material.
 9. The semiconductor-element-including memory device according to claim 1, wherein in the page write operation, a group of positive holes generated by an impact ionization phenomenon are retained inside the channel semiconductor layer, and a voltage of the channel semiconductor layer is made equal to a first data retention voltage that is higher than the voltage of either the first impurity layer or the second impurity layer or that is higher than the voltages of both the first impurity layer and the second impurity layer, and in the page erase operation, the voltages applied to the first impurity layer, the second impurity layer, the first gate conductor layer, and the second gate conductor layer are controlled to discharge the group of positive holes through either the first impurity layer or the second impurity layer or both the first impurity layer and the second impurity layer, and the voltage of the channel semiconductor layer is made equal to a second data retention voltage that is lower than the first data retention voltage. 